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U2010B
Phase Control Circuit for Current Feedback
Description
The U2010B is designed as a phase-control circuit in bipolar technology. It enables load-current detection and has a soft-start function as well as reference voltage output. Motor control with load-current feedback and overload protection are preferred applications.
Features
D Full wave current sensing D Mains supply variation compensated D Programmable load-current limitation
with over- and high-load output
D Internal supply voltage monitoring D Current requirement 3 mA D Temperature compensated reference voltage
v
D Variable soft-start D Voltage and current synchronization D Automatic retriggering switchable D Triggering pulse typical 125 mA
Package: DIP16, SO16
Applications
D Advanced motor control D Grinder D Drilling machine
Block Diagram
96 11646
15 Limiting detector Voltage detector
14 Overload Mains voltage compensation
13
12
11 Supply voltage 10
GND
High load
Automatic retriggering Output Current detector 16 Pulse output 1 Load current detector
100%
70%
amax
A 9
Phase control unit o = f (V4)
-
1
2
+
Full wave rectifier
B Programmable Auto- start overload protection C Imax
Voltage monitoring Level shift
Soft start 4 5 Figure 1. Block diagram 6 7
Reference voltage 8
2
3
TELEFUNKEN Semiconductors Rev. A1, 28-May-96
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Mains Supply
U2010B
General Description
The U2010B contains voltage limiting and can be connected with the mains supply via D1 and R1. Supply voltage between Pin 10 and Pin 11 is smoothed by C1.
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230 V ~ R1 R2 330 kW VS 13 Overload Limiting detector High load Voltage detector Mains voltage compensation Supply voltage 10 GND 12 11 C1 22 m F Load 15 14 BYT51K R8 470 kW LED 18 k W/2 W D1 D3
*
a max
Automatic retriggering 100% Output TIC 226 R3 16 Voltage monitoring 1 Level shift 3 4 5 6 Load current detector 2 R6 R5 3.3 kW ^ V(R6)= 180W R4 3.3 kW Full wave rectifier Current detector 1 2 70%
a max
A 9
Mode
Figure 2. Block diagram with external circuit
*
- + Phase control unit = f (V4 )
o
Programmable overload protection
B Auto- start C Imax
A B C S1
v
$250 mV
C3 10 nF R10 0.15 C4 100 kW Load current compensation
Soft start 7
Reference voltage 8
96 11647
v
w
C5 0.1 m F
mF
R11 1 MW
C2 4.7 m F Overload threshold P1 50 kW Set point R7 8.2 kW
In the case of V6 (70% of overload threshold voltage), Pins 11 and 12 are connected internally whereby VT70, the supply current Vsat 1.2 V. When V6 flows across D3.
TELEFUNKEN Semiconductors Rev. A1, 28-May-96
C7 1 mF
U2010B
Pin Description
Isense Isense Co Control Comp. ILoad Csoft VRef 1 2 3 4 5 6 7 8
95 11406
16 Output 15 VSync. 14 VRo 13 Overload 12 High load 11 VS 10 GND 9 Mode
Pin 1 2 3 4 5 6 7 8 9 10 11 12 13 14 15 16
Symbol Isense Isense Co Control Comp. ILoad Csoft VRef Mode GND VS High load Overload VRo VSync. Output
Function Load current sensing Load current sensing Ramp voltage Control input Compensation output Load current limitation Soft start Reference voltage Mode selection Ground Supply voltage High load indication Overload indication Ramp current adjust Voltage synchronization Trigger output
Series resistance R1 can be calculated as follows: R 1max Vmains VSmax Itot ISmax Ix
+ Mains supply voltage + Maximum supply voltage + Total current consumption = I )I + Maximum current consumption of the IC + Current consumption of the
Smax x
+V
mains
2
- V Smax whereas I tot
ramp is determined by Co and its charging current Io. The charging current can be varied using Ro at Pin 14. The maximum phase angle, max, can also be adjusted by using Ro (minimum current flow angle omin) see figure 4. When the potential on Pin 3 reaches the set point level of Pin 4, a trigger pulse width, tp, is determined from the value of Co (tp = 9 ms/nF). At the same time, a latch is set with the output pulse, as long as the automatic retriggering has not been activated, then no more pulses can be generated in that half cycle. Control input at Pin 4 (with respect to Pin 10) has an active range from V8 to -1 V. When V4 = V8, then the phase angle is at its maximum, max, i.e., the current flow angle is minimum. The minimum phase angle, min, is set with V4 -1 V.
external components
Voltage Monitoring
As the voltage is built up, uncontrolled output pulses are avoided by internal voltage monitoring. Apart from that all the latches in the circuit (phase control, load limit regulation) are reset and the soft-start capacitor is short circuited. This guarantees a specified start-up behavior each time the supply voltage is switched on or after short interruptions of the mains supply. Soft-start is initiated after the supply voltage has been built up. This behavior guarantees a gentle start-up for the motor and automatically ensures the optimum run-up time.
w
Automatic Retriggering
The current-detector circuit monitors the state of the triac after triggering by measuring the voltage drop at the triac gate. A current flow through the triac is recognized, when the voltage drop exceeds a thres hold level of typ. 40 mV. If the triac is quenched within the relevant half-wave after triggering; for example owing to low load currents before or after the zero crossing of current wave or; for commutator motors, owing to brush lifters. Then the automatic retriggering circuit ensures immediate retriggering, if necessary with a high repetition rate, tpp/tp, until the triac remains reliably triggered.
Phase Control
The function of the phase control is largely identical to the well known IC family U211B. The phase angle of the trigger pulse is derived by comparing the ramp voltage V3 which is mains synchronized by the voltage detector with the set value on the control input, Pin 4. The slope of the
TELEFUNKEN Semiconductors Rev. A1, 28-May-96
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U2010B
Current Synchronization
Current synchronization fulfils two functions:
*Monitoring the current flow after triggering. *Avoiding a triggering due to inductive load.
If the mains voltage compensation and the automatic retriggering are not required, both functions can be suppressed by limiting |V15 - 10| 7 V (figure 3).
v
In case the triac extinguishes again or it does not switch on, automatic triggering is activated until the triggering is successful. In the case of inductive load operation the current synchronization ensures that in the new half wave no pulse is enabled as long as there is a current available which from the previous half-wave, which flows from the opposite polarity to the actual supply voltage.
Load Current Compensation
The circuit continuously measures the load current as a voltage drop at resistance R6. The evaluation and use of both half waves results in a quick reaction to load current change. Due to voltage at resistance R6, there is a difference between both input currents at Pins 1 and 2. This difference controls the internal current source, whose positive current values are available at Pins 5 and 6. The output current generated at Pin 5 contains the difference from the load-current detection and from the mains-voltage compensation (see figure 1). The effective control voltage at Pin 4 is the final current at Pin 5 together with the desired value network. An increase of mains voltage causes the increase of control angle , an increase of load current results in a decrease in the control angle. This avoiding a decrease in revolution by increasing the load as well as the increase of revolution by the increment of mains supply voltage.
A special feature of the integrated circuit is the realization of this current synchronization. The device evaluates the voltage at the pulse output between gate and reference electrode of the triac. This results in saving separate current synchronization input with specified series resistance.
Voltage Synchronization with Mains Voltage Compensation
The voltage detector synchronizes the reference ramp with the mains-supply voltage. At the same time, the mains dependent input current at Pin 15 is shaped and rectified internally. This current activates the automatic retriggering and at the same time is available at Pin 5. By suitable dimensioning, it is possible to attain the specified compensation effect. Automatic retriggering and mains voltage compensation are not activated until |V15 - 10| increases to 8 V. Resistance, Rsync. defines the width of the zero voltage cross over pulse, synchronization current, and hence the mains supply voltage compensation current. Mains
96 11648
Load Current Limitation
The total output load current is available at Pin 6. It results in a voltage drop across R11. When the potential of the load current reaches about 70% of the threshold value (VT70) i.e., ca. 4.35 V at Pin 6, it switches the high load comparator and opens the switch between Pins 11 and 12. By using an LED between these pins, (11 and 12) a high load indication can be realized. If the potential at Pin 6 increases to ca. 6.2 V (= VT100), it switches the overload comparator. The result is programmable at Pin 9 (operation mode). Mode selection: a) max (V9 = 0) In this mode of operation, after V6 has reached the threshold VT100, Pin 13 switches to -VS (Pin 11) and Pin 6 to GND (Pin 10). A soft-start capacitor is then shorted and the control angle is switched to max. This position is maintained until the supply voltage is switched off. The motor can be started again with soft-start function when the power is switched on again. As the overload condition switches Pin 13 to Pin 11, it is possible to set in a smaller control angle, max, by connecting a further resistance between Pins 13 and 14.
R2 15 2x BZX55 C6V2
U2010B
10
Figure 3.
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TELEFUNKEN Semiconductors Rev. A1, 28-May-96
U2010B
b) Auto start (Pin 9 open) The circuit behaves as written under max (V9 = 0), with the exception that Pin 6 is not connected to GND. If the value of V6 decreases to 25% of the threshold value (VT25), the circuit becomes active again with soft-start.
*
c) Imax (V9 = V8) When V6 has attained the overload threshold maximum value i.e. V6 = VT100; Pin 13 is switched to Pin 8 (VRef) through the resistance R (= 2 kW) without soft-start capacitor discharging at Pin 7. With this mode of operation, direct load current control (Imax) is possible. A recommended circuit is shown in figure 18.
Absolute Maximum Ratings
Reference point Pin 10, unless otherwise specified Parameters Sink current t Sync. currents t Phase control Control voltage Input current Charging current Soft-start Input voltage Pulse output Input voltage Reference voltage source Output current t 10 ms Load current sensing Input currents Input voltages Overload output High-load output t 10 ms Storage temperature range Junction temperature range Ambient temperature range Pin 11
10 ms
v v
Pin 15
10 ms
"IsyncV "isyncV
-VI II - I max
Symbol -IS -is
Value 30 100 5 20 0 - V8 500 0.5 0 - V8 2 V11 10 30 1 0 - V8 1 30 100 to 125 to
Unit mA mA
Pins 4 and 8 Pin 4 Pin 14 Pins 7 and 8 Pin 16
"
V
mA
mA V V
-VI +VI -VI I0
v
Pin 8
mA
v
Pins 1 and 2 Pins 5 and 6 Pin 13 Pin 12
" Ii
- Vi
IL IL Tstg Tj Tamb
mA V mA mA
C C C
*40 )125 *10 )100
Value 120 180 100
Thermal Resistance
Parameters Junction ambient DIP16 SO16 on p.c. SO16 on ceramic Symbol RthJA Unit K/W
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U2010B
Electrical Characteristics
VS
+ -13 V, T
amb
= 25C, reference point Pin 10, unless otherwise specified Test Conditions / Pins Pin 11 -IS = 3.5 mA -IS = 30 mA -VS = 13.0 V (Pins 1, 2, 8 and 15 open) Pin 8 IL = 10 mA IL = 2.5 mA IS = 2.5 mA IS = 10 mA Pin 11 Symbol -VS -IS Min. 14.5 14.6 Typ. Max. 16.5 16.8 3.2 Unit V mA
Parameters Supply Supply voltage limitation Current requirement Reference voltage source Reference voltage Temperature coefficient
-VRef TCVRef
8.6 8.4
8.9 8.8 -0.004 +0.006 11.3
9.2 9.1
V %/K
Voltage monitoring Turn-on threshold -VSon Phase control - synchronization Pin 15 Input current Voltage sync. syncV Voltage limitation IL = 2 mA syncV Input current Current sync. Pin 16 syncI Reference ramp, figure 4 Charging current Pin 14 -I Start voltage Pin 3 -Vmax Temperature coefficient of Pin 3 TCR start voltage Final voltage Pin 3 -Vmin R - reference voltage I = 10 m Pins 14 and 11 VR Temperature coefficient I = 10 m Pin 14 TCVR I = 1 m Pulse output current V16 = - 1.2 V, figure 5, Pin 16 I0 Output pulse width VS = Vlimit, tp C3 = 3.3 nF, figure 6, Pin 16 Automatic retriggering Repetition rate I15 150 mA tpp Threshold voltage Pin 16 I Soft start, figure 7 and 8 Pin 7 Starting current V7 = V8 -I0 Final current V7-10 = -1V -I0 Discharge current +I0 Output current Pin 4 +I0 Supply voltage compensation, figure 9 Pin 15 Transfer gain I15/ I5 Pin 15/5 Gi (Pins 1 and 2 open) Output offset current V(R6) = V15 = V5 = 0 0 Load current detection, R1 = R2 = 3 kW, V15 = 0, V5 = V6 = V8, figure 10 Transfer gain I5/150 mV, I6/150 mV GI Output offset currents Pin 5, Pin 6 - 8 -I0 Reference voltage I1, I2 = 100 mA Pins 1 and 2 -VRef Shunt voltage amplitude see figure 2 (R6)
12.3 2 9.0 30 100 2.05
V mA V mA
"
"I "V "I
0.15 8.0 3 1 1.85
8.5
1.95
mA V
%/K
(V8 0.96
"200 mV)
1.02 0.03 0.06 125 30
-0.003
1.10
V %/K mA ms
100
150
w
"V
3 20 5 15 0.5 0.2 14
5
7.5 60 15 40 2
tp mV
10 25
mA mA mA mA
17
20 2
"I
mA mA/mV mA mV mV
"V
0.28 0 300
0.32 3
0.37 6 400 250
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TELEFUNKEN Semiconductors Rev. A1, 28-May-96
U2010B
Parameters Load current limitation, High load switching Overload switching Restart switching Test Conditions / Pins Pin 6-8, figs. 11 to 14 Threshold VT70 Threshold VT100 Threshold VT25 Symbol VT70 VT100 VT25 Ii R0 -V9 -I9 I9 Vsat Vlim Min. 4 5.8 1.25 Typ. 4.35 6.2 1.55 Max. 4.7 6.6 1.85 1 8 4.7 20 20 1.0 7.8 Unit V V V
Input current Enquiry mode Output impedance Switching mode Programming input, figure 2, Pin 9 Input voltage - auto-start Pin 9 open Input current V9 = 0 (amax) V9 = V8 (Imax) High load output, VT70, figure 12, I12 = -3 mA, Pin 11-12 Saturation voltages V6-8 VT70 V6-8 VT70 Overload output, VT100, V9 = open or V9 = V10, fig. 13 Leakage current V6-8 VT25 V13 = (V11+1)V Pin 13 Saturation voltages V6-8 VT100, Pins 11-13 I13 = 10 mA Output current, max. load V9 = V8, fig. 13 Pin 13 Leakage current V6 VT100 Pin 13 Output impedance Open collector Pin 13 V6 VT100 Saturation voltage V6-8 VT100, Pin 13 I13 = 10 mA
mA
kW
2 3.8 5 5 0.5 7.0
4 4.3 10 10 0.75 7.4
mA
V
V
v w v w
Ilkg Vsat I13 Ilkg R0 V13-8
120 100
0.5 0.1 1 4 2 4 100 8
mA
V mA
v
mA
kW
w w
mV
250
6.8 nF 200 33 nF 4.7 nF 10 nF
Pulse Output VGT=-1.2V
3.3 nF
2.2 nF
Phase angle a ( )
80 IGT ( mA ) 60 40 20 0
150 100 50 0 0 200 400 600 800 1000
Co/ t = 1.5 nF
0
95 10338
200
400
600
800
1000
96 11797
Ro ( kW )
RGT ( W )
Figure 4.
Figure 5.
TELEFUNKEN Semiconductors Rev. A1, 28-May-96
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U2010B
400 Output Pulse Width Dtp/DCo=9ms/nF 300 I 5 (mA ) t p ( ms ) 0 40
80
200
120 100 Mains Supply 160 Compensation Pins 1 and 2 open Vs=-13V 200 -2 -1
95 10342
Reference Point Pin 10 0 I15 ( mA ) 1 2
0 0
95 10339
10 Co = ( nF )
20
30
Figure 6.
50 Soft Start VS=-13V V6=V8 I5 ( m A ) 200
Figure 9.
Load Current Detection V6=VRef=V8 VS=-13V V15=V10=0V Reference Point Pin 8
40 I 7 (mA )
160
30 Reference Point Pin 8 20 10 0 0 2.5 5.0 V7 ( V ) 7.5 10
120
80 40 0 -400
95 10343
-200
0 V(R6) ( mV )
200
400
95 10340
Figure 7.
12 Reference Point Pin 8 10 8 V (V) 7 2.2mF 6 Co=10mF 4 2 0 0
95 10341
Figure 10.
20 Load Current limitation: Auto Start Operation VS=-13V Pin 9 open Reference Points: V13=Pin 10, V6=Pin 8
1mF -V 13-10 ( V ) Soft Start VS=-13V V6=V8 2 4 t(s) 6 8 10
95 10344
16 4.7mF
12
8 4 0 0 VT25 2 4 VT100 6 V6-8 ( V ) 8 10
Figure 8.
Figure 11.
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TELEFUNKEN Semiconductors Rev. A1, 28-May-96
U2010B
10 High Load Output ( 70% ) I12=-3mA 8 V 11-12 ( V ) PV ( W ) 8 10 Power Dissipation at Series Resistance R1
6
6
4 Reference Point Pin 8 2 VT70 0 0 1 2 3 4 5 6 7
95 10348
4 2 0 0 10 20 30 40 50 V6 ( V ) R1 ( kW )
95 10345
Figure 12.
12 10 -V 13-10 ( V ) 8 6 4 2 0 0
95 10346
Figure 15.
10 Power Dissipation at Series Resistance 8
Load Current limitation: Current Control Operation VS=-13V V9=V8 Reference Points: V13=Pin 10 V6=Pin 8
PV ( W ) VT100 10
95 10350
6
4 2 0 8 0 3 6 9 IS ( mA ) 12 15
2
4 t(s)
6
Figure 13.
20 Load Current limitation: amax Operation VS=-13V V9=V10 Reference Points: V13=Pin 10, V6=Pin 8 R 1max (k W ) 100
Figure 16.
Max. Series Resistance VM=230VX 80
16 V13-10 ( V )
12
60
8 4 0 0 2 4 VT100 6 V6-8 ( V ) 8 10
40 20 0 0 2 4 6 IS ( mA ) 8 10
95 10347
95 10349
Figure 14.
Figure 17.
TELEFUNKEN Semiconductors Rev. A1, 28-May-96
9 (12)
230 V ~
96 11649
18 k W/2 W D1 470 kW BYT51K 22 VS 13 Overload Limiting detector Voltage detector High load GND Mains voltage compensation Supply voltage 10 12 11 C1 1 MW R9 15 14 R8 LED D3 R1 R2 330 kW
U2010B
Application Circuit
10 (12)
L
amax amax mF
Load
Automatic retriggering 100% Output Current detector 1 2 Full wave rectifier 70%
amax
B Auto- start I max C
A 9 S1
TIC 226 16 Voltage monitoring 1 Level shift 3 4 5 6
Phase control unit = f(V4 )
o
- +
Programmable overload protection
A B C
R3
R 12 220 kW
Figure 18.
Load current detector 2 Soft start 7
180 W
R4
BC308 Reference voltage 8 T1
3.3 kW
D2 C5 1N4148
R6 C3 10 nF R 10
^ V (R6) =
"250 mV
C4
0.1 mF 0.15
R 11
R5
mF
1 MW
Overload threshold P1 50 kW Set point R7 8.2 kW
C2 4.7 mF
3.3 kW
C7 1 mF 100 kW Load current compensation R 13 100 kW
1m F
C6
TELEFUNKEN Semiconductors Rev. A1, 28-May-96
N
U2010B
Dimensions in mm
Package: DIP16
94 9128
Package: SO16
94 8875
TELEFUNKEN Semiconductors Rev. A1, 28-May-96
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U2010B
Ozone Depleting Substances Policy Statement
It is the policy of TEMIC TELEFUNKEN microelectronic GmbH to 1. Meet all present and future national and international statutory requirements. 2. Regularly and continuously improve the performance of our products, processes, distribution and operating systems with respect to their impact on the health and safety of our employees and the public, as well as their impact on the environment. It is particular concern to control or eliminate releases of those substances into the atmosphere which are known as ozone depleting substances ( ODSs). The Montreal Protocol ( 1987) and its London Amendments ( 1990) intend to severely restrict the use of ODSs and forbid their use within the next ten years. Various national and international initiatives are pressing for an earlier ban on these substances. TEMIC TELEFUNKEN microelectronic GmbH semiconductor division has been able to use its policy of continuous improvements to eliminate the use of ODSs listed in the following documents. 1. Annex A, B and list of transitional substances of the Montreal Protocol and the London Amendments respectively 2 . Class I and II ozone depleting substances in the Clean Air Act Amendments of 1990 by the Environmental Protection Agency ( EPA) in the USA 3. Council Decision 88/540/EEC and 91/690/EEC Annex A, B and C ( transitional substances ) respectively. TEMIC can certify that our semiconductors are not manufactured with ozone depleting substances and do not contain such substances.
We reserve the right to make changes to improve technical design and may do so without further notice. Parameters can vary in different applications. All operating parameters must be validated for each customer application by the customer. Should the buyer use TEMIC products for any unintended or unauthorized application, the buyer shall indemnify TEMIC against all claims, costs, damages, and expenses, arising out of, directly or indirectly, any claim of personal damage, injury or death associated with such unintended or unauthorized use. TEMIC TELEFUNKEN microelectronic GmbH, P.O.B. 3535, D-74025 Heilbronn, Germany Telephone: 49 ( 0 ) 7131 67 2831, Fax number: 49 ( 0 ) 7131 67 2423
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TELEFUNKEN Semiconductors Rev. A1, 28-May-96

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